• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    ENERGY CONVERSION SYSTEM AND METHOD TO CONTROL AN ENERGY CONVERSION SYSTEM An energy converter (10), control device (20) and methods (100) are presented to drive a permanent magnet motor or other load (6) through a sine wave filter (16) and a transformer (18), in which the inverter output current (IA, IB, IC) is controlled using a current and frequency ratio (24) to convert a frequency value or desired speed (21, 31) at a current setpoint (32), and the inverter output current (IA, IB, IC) is regulated using a control algorithm (26) with a bandwidth below the resonant frequency of the sine wave filter (16).
    公开号:BR102014009688B1
    申请号:R102014009688-4
    申请日:2014-04-23
    公开日:2021-03-16
    发明作者:Jingbo Liu；Thomas Nondahl；Peter Schmidt；Semyon Royak
    申请人:Rockwell Automation Technologies, Inc；
    IPC主号:
    专利说明:

    HISTORIC
    Sensorless motor drives are used in a variety of applications, particularly when providing position and / or speed sensors directly to a motor load, they are difficult and impractical. A typical sensorless system employs a voltage-frequency (T / F) controller, alternatively known as Volts per Hertz (V / Hz) that provides a voltage set point, according to the desired motor speed or frequency and this form of sensorless control was used primarily with induction motors. In certain applications, however, a configuration transformer is generally required to stimulate the motor drive output voltage. For example, a transformer can allow a low voltage drive to be used to power a medium voltage induction motor and / or a configuration transformer can be used to reduce I2R losses and allow the use of a smaller calibrator cable wire for long cables running between the motor drive and the driven motor. Certain applications also employ sine wave filters, such as LC filters to suppress reflected wave voltage spikes associated with variable frequency, pulse amplitude modulated drives. The use of frequency and voltage control techniques, however, can lead to problems, particularly when a transformer and / or sine wave filter is connected between the motor drive at the motor load. For example, frequency and voltage control loops generally suffer from variations in uncontrolled drive current, even when the voltage command is constant. Also, the saturation of the configuration transformer can cause the drive current to be increased significantly, without releasing too much energy to the motor load. In addition, frequency and voltage control in combination with a sine wave filter under start conditions can result in the motor not being able to start, with large fluctuations in the rotor axis for low frequency commands. In addition, voltage and frequency drive control, without a conventional sensor, has not been widely successful in driving permanent magnet motors, when output filters and transformers are employed. Thus, although sensorless control schemes are advantageous, due to the length of the cable runs and avoid costs associated with providing feedback directly from the motor, further improvements are necessary for sensorless motor drive control, particularly for driving motor motors. permanent magnet. SUMMARY
    Several aspects of the present disclosure are now summarized to facilitate a basic understanding of the disclosure, in which this summary is not an extensive overview of the disclosure and is not intended to identify certain elements of the disclosure or to outline its scope. On the contrary, the primary objective of this summary is to present the various concepts of revelation in a simplified form before the more detailed description that is presented hereinafter. The present disclosure provides sensorless position control using current regulation and current frequency control and reduced bandwidth control concepts, by which open loop power converter control is possible to avoid or mitigate the disadvantages mentioned above. control without traditional frequency and voltage sensor. These techniques and apparatus find particular utility in association with sensorless motor drive applications involving sine wave output filters and configuration transformers to accommodate long cable runs between the drive and a driven motor, including induction motors and / or permanent magnet motors, as in submersible pump applications and the like. Other applications are possible, in which the described control approaches can be used, including operation of a power converter to provide variable frequency AC output to any form of load.
    A power conversion system is presented, which includes an inverter that provides AC output power to drive a load, as well as a controller that regulates the inverter output current (s) in whole or in part, according to with a frequency or speed setpoint value through a control algorithm that has a bandwidth below a resonant frequency of a filter coupled between the inverter and the load. In certain embodiments, the controller includes a current frequency control component providing a current setpoint value, at least partially, according to the frequency or speed setpoint, as well as a current control regulator component that implements the control algorithm to regulate the current or currents of implementations, the current control regulator can be an integral proportion controller (PI) with a control bandwidth below the resonant frequency of the output filter and the control can be implemented to regulate the inverter output currents, according to the current setpoint value and one or more feedback signals or values that represent the inverter output current. In addition, certain implementations of the controller include a rate limiting component operated to limit a rate of change from the desired frequency or speed value, received to provide a rate-limited frequency or speed setpoint.
    A method of controlling the energy conversion system and computer-readable media with computer-executable instructions are provided, in accordance with additional aspects of the present disclosure, in which a current setpoint value is determined, at least in part, according to a frequency or speed setpoint value and at least one AC output current feedback signal or value from the power conversion system is sampled. The method also includes the regulation of the output current, according to the current setpoint value and the output current feedback using a control algorithm with a bandwidth below a resonant frequency of an output filter. In certain implementations, the method further includes limiting the rate of change to a desired frequency or speed value to determine the frequency or speed setpoint and may also include determining the current setpoint value, according to a relationship of current and frequency with a value of zero current, corresponding to a value of zero frequency. In certain implementations, for example, the current and frequency ratio can be a curve or parametric equation or look-up table or the like, including a first part with increasing current values corresponding to a first frequency variation from zero to a limit frequency, as well as a second part having a constant current value, such as a maximum inverter output current, for a frequency above the limit frequency value. BRIEF DESCRIPTION OF THE DRAWINGS
    The following description and drawings set out certain illustrative implementations of the disclosure in detail, which are indicative of the various ways in which the various principles of the disclosure can be realized. The illustrative examples, however, are not complete with the many possible achievements of the revelation. Other objectives, advantages and innovative aspects of the disclosure will be established in the following detailed description, when considered together with the drawings, in which-.
    Figure 1 is a schematic diagram illustrating an exemplary variable frequency drive type energy conversion system that provides AC output power through a sine wave filter and a configuration transformer and cable for a motor load permanent magnet drive for submersible pump and similar applications, where the motor drive inverter output stage is controlled using a frequency and current control component and an integral bandwidth ratio (Pl) control component reduced, according to. one or more aspects of the present disclosure, -
    Figure 2 is a schematic diagram illustrating additional details of the exemplary inverter controller in the system of Figure 1, including a rate limiting component, a frequency and current control component and a reduced bandwidth PI control component, according to the revelation, - and
    Figure 3 is a flow chart illustrating an exemplary method for controlling an energy conversion system that drives a load through a filter, in accordance with additional aspects of the present disclosure. DETAILED DESCRIPTION
    Referring now to the figures, several achievements or implementations are hereinafter described in conjunction with the drawings, in which similar reference numbers are used to refer to completely similar elements, and in which the different aspects are not necessarily drawn in . scale. The present disclosure provides methods and apparatus for driving an electric motor or other load through an output filter and, optionally, through an additional transformer, and finds use in situations of submerged pump or other applications, in which an AC load is fed without direct feedback from the driven load. For example, sensorless motor drive applications can be enhanced by using the device and revealed methods, even for permanent magnet motor loads, while decreasing or avoiding unregulated drive output current, transformer saturation and problems with starting motor, seen in conventional motor drive systems without sensor, frequency and voltage. Likewise, the advantages of sensorless control can be facilitated, including reduced system cost and complexity, in combination with the use of sine wave filters and transformers to reduce the cost and size of cabling and to reduce reflected wave problems , while still achieving improved control capabilities in relation to engine speed and / or position or other driven load performance parameters. Furthermore, the concepts of the present disclosure do not require additional hardware and, therefore, present a low-cost solution to the problems mentioned above, associated with motor control schemes without conventional frequency and voltage sensors.
    Figure 1 illustrates an exemplary system 2 having an AC4 power source that provides three-phase AC input power (e.g., 480 V AC, 50 or 60 Hz) to a motor drive energy conversion system 10. The motor drive 10, in turn, provides AC output power, of multiple phases, of variable amplitude and variable frequency through a sine wave filter 16 and a connected transformer 18 and then through a cable 8 to drive a permanent magnet or induction motor load 6, as shown. In several applications, such as submersible pumps, a relatively long cable 8 can be used and transformer 18 can be used in certain implementations, as a lifting device to reinforce the voltage outputs provided by the motor drive 10 at a higher level to combat I2R losses along the length of the cable 8 and reduce the size of the cable 8 and / or to allow a relatively low voltage motor drive to operate a higher voltage motor load 6. As seen in Figure 1, the motor 10 includes a rectifier 12, which can be an active rectifier (for example, alternating) or a passive rectifier, full wave, half wave etc., which receives AC input energy from source 4 and supplies DC power to a bus or DC 13 connecting circuit having a capacitance C. Although illustrated as a multi-phase rectifier, the concepts of the present disclosure can be used in input drive or power converters going from single stage. An inverter 14 receives DC power from the bus circuit 13 and includes switching devices SI, S2, S3, S4, S5 and S6 operated in accordance with the inverter switching control signals 22 provided by a controller 20, in order to convert DC power in AC IA, IB and IC output currents to drive the motor load 6. In the illustrated embodiment, inverter 14 provides a three-phase output, but other multi-phase or single-phase implementations are possible within the scope of the present revelation. Any suitable S1-S6 inverter switching devices may be used, including, but not limited to, isolated gate bipolar transistors (IGBTs), silicon controlled rectifiers (SCRs), gate disable thyristors (GTOs), integrated port switched thyristors (IGCTs) etc.
    The motor drive 10 also includes a controller 20 that provides the inverter toggle control signals to the S1-S6 inverter keys. Controller 20 and its elements and components (for example, additionally shown in Figure 2 below) can include a suitable or processor-based logic circuitry and may also include signal level amplification and / or driver circuitry (not shown) to provide adequate drive voltage and / or current levels sufficient to selectively drive switching devices S1-S6, for example, as comparators, transmitter wave generators or digital logic elements / processor and signal drivers. In addition, controller 20 can provide toggle control signals 22 in accordance with any suitable pulse amplitude modulation technique, including, but not limited to, vector modulation (SVM), transmitter-based pulse amplitude modulation, selective harmonic elimination (SHE) etc.
    System 2 in Figure 1 also includes a sine wave filter or output filter 16, in one example, a three-phase LC filter having an LF series filter inductor on each output line, as well as a CF filter capacitor corresponding between the corresponding phase line and a common connection point. Other output filter topologies can be used, such as LCL filters, CLC filters, etc. with one or more standard elements and additional filter elements (for example, CF filter capacitors) connected in any suitable delta or Y configuration. In addition, as shown in Figure 1, a transformer 18 is provided between the filter 16 and the motor cable 8. In the illustrated example, transformer 18 has a primary connected by delta phase, as well as a secondary connected in Y, although any suitable primary and / or secondary transformer winding configuration or topology can be used. In addition, transformer 18 may, but need not, be a lift transformer. In certain applications, a lift transformer 18 is advantageous, for example, to allow a low voltage drive 10 to power a medium or high voltage motor 6 or to allow the use of a medium voltage drive to power a high voltage motor voltage 6. Also or in combination, an elevation transformer 18 can be useful to allow a reduction in the current levels transmitted by the cable 8, thereby facilitating the use of smaller diameter cable wires and a corresponding reduction in power losses. 12R on the cable 8. The cable 8, in addition, can be of any suitable construction to interface the motor drive output, the sine wave filter 16 and the transformer 18 with the motor conductors 6.
    Motor drive 10 and its controller 20 operate without a sensor to control one or more operating parameters of the driven motor load 6. For example, controller 20 provides inverter switching control signals 22 in order to control the position and / or speed and / or torque of the motor 6, without directly feeling any of these controlled parameters. In the illustrated implementation, for example, current sensors 27 are provided at the inverter output 14 to provide signals or feedback values 28 to the controller 20 that represent the inverter output currents IA, IB and IC and / or of which the values of these Output currents can be computed, derived or otherwise estimated. Any suitable current sensitivity devices 27 can be used to generate the signals and / or values 28 and can provide analog signals 28 and / or the sensors 27 can be intelligent sensors that provide digital values 28 representing the output currents IA, IB and IC provided by the inverter.
    The controller 20 uses the feedback signals or values 28 as well as one or more desired operating parameters 21 to perform the regulation of the output currents IA, IB and IC in a localized closed loop manner. In general, however, the control technique implemented by controller 20 is essentially sensorless or open loop in relation to the actual operating condition of the driven motor load 6, since there are no direct feedback signals obtained from the motor 6 itself . In the example in Figure 1, for example, controller 20 receives a frequency or motor speed value / * 21 from a supervisor control system component (not shown) that can be a distributed control system element, a button adjustable by user, local user interface etc. Controller 20, moreover, includes a frequency and current control component 24 as well as an integral reduced bandwidth ratio (PI) controller 26, as further described below. In operation, control components 24 and 26 are used to regulate the inverter output currents IA, IB and IC by generating the alternating control signals of inverter 22, according to the speed or frequency signal or value desired 21 and the feedback signals or values 28.
    Referring also to Figure 2, an embodiment of the controller 20 is illustrated, which can optionally include a rate limiter 30 as well as the current and frequency control component (IF) 24 and the controller element PI 26 in one path. control loop forward. If included, the rate limiting component 30 receives the desired frequency or speed value 21 and limits its rate of change to provide a frequency or speed setpoint value 31 as an input to the frequency current control component 24. Other embodiments are possible, in which the rate limiter 30 is omitted, with the frequency and current component 24 directly receiving the desired frequency or speed signal 21 as a setpoint input. In the illustrated implementation, the signal or output value of the rate limiter 30 is a rate or speed setpoint value or rate-limited rate 31 (for example, / RL) and the rate limiting component 30 can be any hardware suitable, software run by processor, firmware run by processor, programmable logic, analog circuitry, etc. which limits the rate of change of the desired speed or frequency signal received 21.
    In a possible implementation, for example, the rate limiter 30 limits the rate of change of the speed signal 21, so that the output signal 31 is at a frequency that changes no faster than the maximum acceleration capacity of the motor 6 For example, the sine wave filter 16 may have a resonant frequency (determined according to the inductance of the LF filter inductors and the capacitance of the CF filter capacitors) of several hundred HZ (for example, about 4000 Hz in one example), with the rate limiter 30 operating to limit the rate of change of the received signal 21 to a few tens of cycles per second (e.g., about 20-30 Hz or less, in one embodiment). In operation, a step change in the received signal 21 will be changed to a slope signal 31 and thus the rate limiter 30 prevents the subsequent frequency and current control component 24 from requiring an immediate change to the high current. frequency. In particular, when used with an output sine wave filter 16 and / or a transformer 18, an immediate change to high frequency current output may not cause the motor load 6 to rotate. The use of rate limiter 30, in certain embodiments, advantageously limits the rate of change of the frequency setpoint below the value at which the motor load 6 can accelerate to the desired rate.
    The rate or speed setpoint value, rate limited 31 is provided as an input to the frequency and current control component 24 as well as an integration system 40, 42, as further described below. The frequency and current control component (l-F) 24 receives the rate or speed limited rate setpoint 31 and generates an δ (i * a) 32 axis current setpoint in the same way. As shown in Figure 2, controller 20 implements several components, for example, in software or firmware executed by a processor, and operates on certain variables in a reference structure of δr y synchronous, with signals or feedback values received 28 and signals of alternation control generated 22 referring to a fixed reference structure (for example, a, b, c). In this respect, the illustrated δ, y reference structure rotates at the same frequency as the conventional field switching control reference structure (D, Q), but the position need not be the same, with y δ somewhat analogous to "d" and "q", but are not necessarily aligned (for example, probably, y will be somewhere between the D axis and the Q axis, eye δ are orthogonal to each other). It is also understood that the current regulation can be carried out on other reference structures.
    As seen in Figure 2, the frequency and current control component 24 provides a current setpoint output 32 based on the received frequency (or rate-limited) signal or speed setpoint value 31. In a possible implementation, the. frequency and current control 24 implements a double variation curve or function, as illustrated, with the current and frequency ratio being one. zero current value corresponding to a zero frequency value (for example, 0 Hz). As shown in Figure 2, the current and frequency relationship implemented by the control component 24 includes a first part with increasing current values corresponding to a first frequency variation from the zero frequency value to a FCUTÍ limit frequency value as well as a second part with a constant current value (for example, IMAX) corresponding to frequencies above the FCÜT limit frequency, in which IMAX can be the maximum inverter output current 14 in certain implementations and the FCUT limit frequency is preferably adjusted to match at a very low operating frequency of the motor 6 (for example, about 0.5 - 1.0 Hz in an implementation). The frequency and current control component 24, in certain embodiments, can be implemented using a look-up table or a parametric function. In this respect, the current and frequency ratio advantageously avoids the supply of current to the transformer 18 and the motor 6 at zero frequency and includes the first part tilted to the limit frequency, after which the maximum current is demanded, with therefore, the control component 24 avoids sending DC to transformer 18. The control component IF 24 therefore avoids sending DC to transformer 18, and motor load 6 is typically operated at maximum current thereby Motor drive operation is quite different from the conventional voltage frequency approach of previous sensorless drives.
    The output of the current and frequency controller 24 is the axis current set point 8 32, which is provided to the control component PI 26. The control PI is not a strict necessity of all the achievements of the present disclosure, in which any The appropriate current regulation algorithm can be used to regulate the inverter output currents IA, IB and IC in an algorithm bandwidth that is less than the resonant frequency of the sine wave filter 16. In the illustrated embodiment, the controller P1 26 operates according to a y-axis value of zero 33 (i * z = 0), although it is not a strict requirement for all implementations of the present disclosure. The PI 26 controller can be any suitable implementation of well-known integral proportion control algorithms, but the control algorithm is bandwidth limited. Also, the control component 26 can be a PID controller with the corresponding derivative gain (KD) set to zero. The inventors realized that limiting the bandwidth of the PI 2 6 controller prevents or reduces the large inrush current during activation, particularly when drive 10 is providing output currents through a sine wave filter, it will make the output inverter particularly susceptible to large inrush currents and will limit the bandwidth of the PI 26 controller (or other current regulation control algorithm, implemented by controller 20) to be well below the resonant frequency of the sine wave filter helping to reduce or avoid high inrush current levels, particularly at startup.
    The reduced bandwidth PI controller 26 also receives feedback from the inverter output 14 from integrated output current sensors 27. The illustrated controller 20 includes a fixed to synchronous reference frame converter component 44 (a, b, c - > δ, y) that provides current feedback values 5 y and 46 and 48 (ig and iz), converted from the inverter output phase currents felt IA, IB and IC as inputs to the PI 26 controller. The converter 44, in addition In addition, it performs the conversion of the reference structure, according to a signal or phase angle value θ 43, which is computed, in the illustrated embodiment, based on the signal or rate setpoint value or rate limited speed 31 as the frequency integral (0 (2L1 * fRL) by means of a multiplier component 40 that generates the frequency signal d) 41 and an integrating component 42 that provides the signal or phase angle value θ 43. The PI 26 controller In addition, it provides signal or point value outputs of axis tension adjustment δ and y Vg and Vr 35 and 34, respectively, which are converted to the fixed reference structure by converter 36 (δ, 7 -> a, b, c) using the phase angle value or sign θ 43. The reference structure converter 36, in turn, provides a set of three fixed reference structure voltage setpoint signals or values 37 (Va, Vb and Vc) as inputs to a modulation component of pulse amplitude (PWM) 38 which includes any suitable form of modulation, isolation, amplifiers, driver circuits, etc. to generate inverter toggle control signals 22 using known techniques.
    In certain embodiments, the bandwidth of the PI or another regulation control algorithm, implemented in the control component 26, is well below the resonant frequency of the associated sine wave filter 16. In this respect, servo and / or control algorithms Conventional motor drive motors regulate the current using a relatively high bandwidth, as in the order of 1 kHz. However, as mentioned above, this high bandwidth of the control algorithm can lead to instability or inability to properly control the output currents provided to the motor load 6 and / or lead to undesirable saturation of transformer 18 and current problems. excessive starting. According to the present disclosure, the bandwidth of the PI 26 controller is preferably one or more orders of magnitude less than the resonant frequency of the sine wave filter 16. For example, the bandwidth of the PI controller can be in the order of about 20 Hz or 30 Hz for use in conjunction with sine wave filters 16 which have a resonant frequency of about 2 kHz to 6 kHz. This can be implemented, for example, by limiting the proportional and integral gains (for example, KP and Kl) used in the regulation algorithm of the PI 26 controller. The output of the PI 26 controller, in this respect, can be implemented as the sum of the error between the current setpoint values 32 and 33 and the corresponding feedback values 46 and 48, multiplied by KP proportional constant added to the error integral multiplied by the integral constant Kl. Thus, in specific realizations, the amplitude of the current loop regulation band is significantly below the resonant variation of the filter 16 and this can be implemented by maximums or limits in the values of Kl and KP used in the PI 26 algorithm, so that the resonant point of the entire closed loop is less than about 20 or 30 Hz in certain implementations. Thus, the current regulation algorithm implemented by controller 20 will not attempt to regulate the current above about 30 Hz. The outputs 34, 35 of the PI 26 controller are the synchronous reference structure voltage values 34 and 35, which are, then, translated into fixed three-phase reference frame values 37 that pulse amplitude is used that modulates inverter alternations S1-S6.
    Referring also to Figure 3, a flow chart is provided, which illustrates a method 100 for controlling an energy conversion system (for example, the motor drive 10 above) to drive a load (for example, the motor 6) through of a filter (for example, sine wave filter 16). Although exemplary method 100 is portrayed and described in the form of a series of actions or events, it will be appreciated that various methods of disclosure are not limited by the illustrated order of those actions or events, except as specifically set forth here. In this respect, except as specifically provided hereinafter, some actions or events may occur in a different order and / or simultaneously with other actions or events in addition to those illustrated and described here and not all the illustrated steps may be necessary to implement a process or method, in according to the present disclosure. The illustrated methods can be implemented in hardware, software executed by processor or combinations of these, in order to provide sensorless motor control using limited bandwidth control algorithms described here and several accomplishments or implementations include non-transitory computer-readable means having computer executable instructions that perform the illustrated and described methods. For example, method 100 can be implemented using one or more processors associated with controller 20, by executing instructions stored in an electronic memory operatively associated with controller 20.
    Process 100 starts at 102, where a desired frequency or speed value is updated (for example, signal or f * 21 value in Figures 1 and 2 above). At 104, the desired value can be optionally rate limited to provide a frequency setpoint value or rate limited speed (for example, / RL 31 in Figure 2), at least partially according to the setpoint value. frequency or speed setting 21, 31. In 108, one or more AC output current feedback signals or values from the power converter are sampled (for example, IA, IB and IC sampled using sensors 27 in Figure 1 above). At 110, the AC output current (s) is (are) regulated, according to the current setpoint value 32 and the signal (s) or value (s) of feedback 28 using a control algorithm having a bandwidth below the resonant frequency of the filter 16. For example, the AC output currents are regulated in the motor drive 10 described above, using integral proportion control algorithm (for example, by middle of the PI 26 controller) having a bandwidth that is less than the resonant frequency of the sine wave filter 16. The process 100, in Figure 3, then returns to receive another desired frequency or speed value, updated 21 in 102, and continues as described above.
    The above techniques and apparatus therefore advantageously facilitate the sensorless control of induction motor or permanent magnet 6 loads in applications such as those described above, in which sine wave filters 16 and / or transformers 18 are provided to accommodate long lengths of cable 8 without the disadvantages associated with conventional voltage and frequency control schemes. In addition, the revealed concepts can be used without any additional hardware and can be widely implemented in software run by the processor of a motor drive controller 20. Furthermore, these techniques can be employed to reduce or avoid filter inrush current, saturation of transformer and uncontrolled motor drive output current oscillation, associated with conventional approaches, while avoiding extra cost and / or system complexity associated with the provision of sensors on load 6. In addition, the techniques also allow system design flexibility employing transformers 18 to accommodate long cable runs, while reducing or preventing I2R losses and allowing the use of smaller cabling 8, thereby providing viable solutions for submersible pump applications and other installations in which transformer 18 can accommodate the use of low voltage motor drive 10 for medium voltage motors or higher 6, including permanent magnet motors.
    The above examples are merely illustrative of several possible realizations of various aspects of the present disclosure, in which equivalent changes and / or modifications will occur to the technicians in the subject, through the reading and understanding of this specification and the attached drawings. In particular with regard to the various functions performed by the components described above (assemblies, devices, systems, circuits and the like), the terms (including a reference to a "medium") used to describe these components are intended to correspond, unless otherwise stated. any form, such as hardware, software executed by computer or combinations thereof, that performs the specific function of the described component (that is, that is functionally equivalent) even if not structurally equivalent to the revealed structure that performs the function in the illustrated implementations of revelation. In addition, although a particular aspect of the disclosure may have been revealed in relation to only one of several implementations, that aspect can be combined with one or more other aspects of the other implementations, as may be desired and advantageous for any particular application or particular. Also, insofar as the terms "including", "having", "has", "with" or its variants are used in the detailed description and / or in the claims, these terms are intended to be inclusive, similarly to the term "understanding".
    权利要求:
    Claims (10)
    [0001]
    1. ENERGY CONVERSION SYSTEM (10), comprising: an inverter (14) including a plurality of alternating devices (S1-S6) operable according to alternating control signals (22) to provide AC output power to drive a charge (6); and a controller (20) that provides the alternating control signals (22) to the inverter (14) to regulate the inverter output currents (IA, IB, IC), at least partially, according to a set point value frequency or speed adjustment (21, 31) by means of a controller (26), characterized in that the controller (26) has a bandwidth one or more orders of magnitude less than that of a resonant frequency of a filter (16) coupled between the inverter (14) and the load (6).
    [0002]
    2. ENERGY CONVERSION SYSTEM (10), according to claim 1, in which the controller (20) is characterized by comprising: a frequency and current control component (24) that provides a setpoint value of current (32), according to the frequency or speed setpoint value (21, 31); and a current control regulator component (26) that implements the control algorithm to regulate the inverter output currents (IA, IB, IC), at least partially, according to the current setpoint value (32 ).
    [0003]
    3. ENERGY CONVERSION SYSTEM (10), according to any one of claims 1 or 2, characterized by the controller (20) regulating the converter output currents (IA, IB, IC) through the controller (26), in accordance with according to a current setpoint value (32) determined according to a current and frequency ratio with a zero current value corresponding to a zero frequency value.
    [0004]
    ENERGY CONVERSION SYSTEM (10), according to any one of claims 1 to 3, characterized in that the controller (20) includes an integral proportion controller (PI) (26) to regulate the inverter output currents (IA , IB, IC), the integral proportion controller (PI) (26) having a bandwidth below the resonant frequency of the filter (16) coupled between the inverter (14) and the load (6).
    [0005]
    5. ENERGY CONVERSION SYSTEM (10), according to any one of claims 1 to 4, characterized by the controller (20) regulating the inverter output currents (IA, IB, IC) according to a set point value current adjustment (32), derived from the frequency or speed setpoint value (21, 31) and according to at least one signal or feedback value (46, 48) representing the inverter output currents (IA , IB, IC).
    [0006]
    ENERGY CONVERSION SYSTEM (10) according to any one of claims 1 to 5, characterized in that the controller (20) comprises a rate limiting component (30) that limits a rate of change of a frequency or speed value desired received (21) to provide the frequency or speed setpoint value (31).
    [0007]
    7. METHOD (100) TO CONTROL AN ENERGY CONVERSION SYSTEM (10) THAT DRIVES A LOAD (6) THROUGH A FILTER (16), method (100) comprising: determining a current setpoint value (32), at least partially, according to a frequency or speed setpoint value (21, 31); sampling at least one AC output current feedback signal or value (IA, IB, IC) from the energy conversion system (10); and regulation of at least one AC output current (IA, IB, IC), according to the current setpoint value (32), and the at least one AC output current feedback signal or value (IA , IB, IC) using a controller (26), characterized in that the controller (26) has a bandwidth of one or more orders of magnitude less than a resonant frequency of the filter (16).
    [0008]
    METHOD (100) according to claim 7, characterized by limiting a rate of change of a desired frequency or speed value (21) to determine the frequency or speed setpoint value (31) .
    [0009]
    9. METHOD (100) according to either of claims 7 or 8, characterized in that at least one AC output current (IA, IB, IC) is regulated using an integral proportion controller (26) having a bandwidth below the filter's resonant frequency (16).
    [0010]
    10. METHOD (100) according to any one of claims 7 to 9, characterized in that the inverter output currents (IA, IB, IC) are regulated according to a current setpoint value (32) determined according to according to a current and frequency relation with a zero current value corresponding to a zero frequency value.
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    同族专利:
    公开号 | 公开日
    EP2797220A1|2014-10-29|
    CN104124883A|2014-10-29|
    US20140312811A1|2014-10-23|
    EP2797220A3|2015-03-25|
    US9054621B2|2015-06-09|
    US9312779B2|2016-04-12|
    CN104124883B|2017-11-07|
    EP2797220B1|2020-02-19|
    US20150194901A1|2015-07-09|
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    法律状态:
    2017-10-03| B03A| Publication of an application: publication of a patent application or of a certificate of addition of invention|
    2018-11-13| B06F| Objections, documents and/or translations needed after an examination request according art. 34 industrial property law|
    2020-02-18| B06U| Preliminary requirement: requests with searches performed by other patent offices: suspension of the patent application procedure|
    2021-01-05| B06A| Notification to applicant to reply to the report for non-patentability or inadequacy of the application according art. 36 industrial patent law|
    2021-02-23| B09A| Decision: intention to grant|
    2021-03-16| B16A| Patent or certificate of addition of invention granted|Free format text: PRAZO DE VALIDADE: 20 (VINTE) ANOS CONTADOS A PARTIR DE 23/04/2014, OBSERVADAS AS CONDICOES LEGAIS. |
    优先权:
    申请号 | 申请日 | 专利标题
    US13/868,216|US9054621B2|2013-04-23|2013-04-23|Position sensorless open loop control for motor drives with output filter and transformer|
    US13/868,216|2013-04-23|
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